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1 lt1206 250ma/60mhz current feedback amplifier d u escriptio s f ea t u re n 250ma minimum output drive current n 60mhz bandwidth, a v = 2, r l = 100 w n 900v/ m s slew rate, a v = 2, r l = 50 w n 0.02% differential gain, a v = 2, r l = 30 w n 0.17 differential phase, a v = 2, r l = 30 w n high input impedance, 10m w n wide supply range, 5v to 15v n shutdown mode: i s < 200 m a n adjustable supply current n stable with c l = 10,000pf the lt1206 is a current feedback amplifier with high output current drive capability and excellent video char- acteristics. the lt1206 is stable with large capacitive loads, and can easily supply the large currents required by the capacitive loading. a shutdown feature switches the device into a high impedance, low current mode, reducing dissipation when the device is not in use. for lower bandwidth applications, the supply current can be reduced with a single external resistor. the low differen- tial gain and phase, wide bandwidth, and the 250ma minimum output current drive make the lt1206 well suited to drive multiple cables in video systems. the lt1206 is manufactured on linear technologys proprietary complementary bipolar process. typical applicatio s u noninverting amplifier with shutdown lt1206 ? ta02 v s = 15v r l = r f = r g = 3k applicatio s u n video amplifiers n cable drivers n rgb amplifiers n test equipment amplifiers n buffers + lt1206 s/d** 15v 15v c comp 0.01 m f* r f r g v in 5v 24k 15v enable v out optional, use with capacitive loads ground shutdown pin for normal operation * ** lt1206 ?ta01 comp 74c906 large-signal response, c l = 10,000pf
2 lt1206 a u g w a w u w a r b s o lu t exi t i s supply voltage ..................................................... 18v input current .................................................... 15ma output short-circuit duration (note 1) ....... continuous specified temperature range (note 2) ...... 0 c to 70 c operating temperature range lt1206c ........................................... C 40 c to 85 c junction temperature ......................................... 150 c storage temperature range ................. C 65 c to 150 c lead temperature (soldering, 10 sec)................. 300 c electrical characteristics symbol parameter conditions min typ max units v os input offset voltage t a = 25 c 3 10 mv l 15 mv input offset voltage drift l 10 m v/ c i in + noninverting input current t a = 25 c 2 5 m a l 20 m a i in C inverting input current t a = 25 c 10 60 m a l 100 m a e n input noise voltage density f = 10khz, r f = 1k, r g = 10 w , r s = 0 w 3.6 nv/ ? hz +i n input noise current density f = 10khz, r f = 1k, r g = 10 w , r s = 10k 2 pa/ ? hz Ci n input noise current density f = 10khz, r f = 1k, r g = 10 w , r s = 10k 30 pa/ ? hz r in input resistance v in = 12v, v s = 15v l 1.5 10 m w v in = 2v, v s = 5v l 0.5 5 m w c in input capacitance v s = 15v 2 pf input voltage range v s = 15v l 12 13.5 v v s = 5v l 2 3.5 v q ja = 100 c/w q ja ? 60 c/w part marking 1206 order part number order part number order part number 1 2 3 4 8 7 6 5 top view nc in +in s/d* v + out v comp n8 package 8-lead plastic dip 1 2 3 4 8 7 6 5 top view v + out v comp v + in +in s/d* s8 package 8-lead plastic so order part number lt1206cn8** lt1206cr** lt1206cs8** LT1206CY** wu u package / o rder i for atio *ground shutdown pin for normal operation **see note 2 v cm = 0, 5v v s 15v, pulse tested, v s/d = 0v, unless otherwise noted. out v comp v + s/d* +in ?n r package 7-lead plastic dd front view 7 6 5 4 3 2 1 tab is v + q ja ? 30 c/w y package 7-lead to-220 out v comp v + s/d* +in ?n front view 7 6 5 4 3 2 1 tab is v + q jc = 5 c/w
3 lt1206 electrical characteristics symbol parameter conditions min typ max units cmrr common-mode rejection ratio v s = 15v, v cm = 12v l 55 62 db v s = 5v, v cm = 2v l 50 60 db inverting input current v s = 15v, v cm = 12v l 0.1 10 m a/v common-mode rejection v s = 5v, v cm = 2v l 0.1 10 m a/v psrr power supply rejection ratio v s = 5v to 15v l 60 77 db noninverting input current v s = 5v to 15v l 30 500 na/v power supply rejection inverting input current v s = 5v to 15v l 0.7 5 m a/v power supply rejection a v large-signal voltage gain v s = 15v, v out = 10v, r l = 50 w l 55 71 db v s = 5v, v out = 2v, r l = 25 w l 55 68 db r ol transresistance, d v out / d i in C v s = 15v, v out = 10v, r l = 50 w l 100 260 k w v s = 5v, v out = 2v, r l = 25 w l 75 200 k w v out maximum output voltage swing v s = 15v, r l = 50 w , t a = 25 c 11.5 12.5 v l 10.0 v v s = 5v, r l = 25 w , t a = 25 c 2.5 3.0 v l 2.0 v i out maximum output current r l = 1 w l 250 500 1200 ma i s supply current v s = 15v, v s/d = 0v, t a = 25 c2030ma l 35 ma supply current, r s/d = 51k (note 3) v s = 15v, t a = 25 c1217ma positive supply current, shutdown v s = 15v, v s/d = 15v l 200 m a output leakage current, shutdown v s = 15v, v s/d = 15v l 10 m a sr slew rate (note 4) a v = 2, t a = 25 c 400 900 v/ m s differential gain (note 5) v s = 15v, r f = 560 w , r g = 560 w , r l = 30 w 0.02 % differential phase (note 5) v s = 15v, r f = 560 w , r g = 560 w , r l = 30 w 0.17 deg bw small-signal bandwidth v s = 15v, peaking 0.5db 60 mhz r f = r g = 620 w , r l = 100 w v s = 15v, peaking 0.5db 52 mhz r f = r g = 649 w , r l = 50 w v s = 15v, peaking 0.5db 43 mhz r f = r g = 698 w , r l = 30 w v s = 15v, peaking 0.5db 27 mhz r f = r g = 825 w , r l = 10 w v cm = 0, 5v v s 15v, pulse tested, v s/d = 0v, unless otherwise noted. beyond 0 c to 70 c. industrial grade parts tested over C 40 c to 85 c are available on special request. consult factory. note 3: r s/d is connected between the shutdown pin and ground. note 4: slew rate is measured at 5v on a 10v output signal while operating on 15v supplies with r f = 1.5k, r g = 1.5k and r l = 400 w . note 5: ntsc composite video with an output level of 2v. the l denotes specifications which apply for 0 c t a 70 c. note 1: applies to short circuits to ground only. a short circuit between the output and either supply may permanently damage the part when operated on supplies greater than 10v. note 2: commercial grade parts are designed to operate over the temperature range of C 40 c to 85 c but are neither tested nor guaranteed
4 lt1206 s all - sig al ba dwidth wu u i s = 20ma typical, peaking 0.1db i s = 10ma typical, peaking 0.1db i s = 5ma typical, peaking 0.1db C 3db bw C 0.1db bw a v r l r f r g (mhz) (mhz) v s = 5v, r sd = 22.1k C 1 150 604 604 21 10.5 30 715 715 14.6 7.4 10 681 681 10.5 6.0 1 150 768 C 20 9.6 30 866 C 14.1 6.7 10 825 C 9.8 5.1 2 150 634 634 20 9.6 30 750 750 14.1 7.2 10 732 732 9.6 5.1 10 150 100 11.1 16.2 5.8 30 100 11.1 13.4 7.0 10 100 11.1 9.5 4.7 C 3db bw C 0.1db bw a v r l r f r g (mhz) (mhz) v s = 15v, r sd = 121k C 1 150 619 619 25 12.5 30 787 787 15.8 8.5 10 825 825 10.5 5.4 1 150 845 C 23 10.6 30 1k C 15.3 7.6 10 1k C 10 5.2 2 150 681 681 23 10.2 30 845 845 15 7.7 10 866 866 10 5.4 10 150 100 11.1 15.9 4.5 30 100 11.1 13.6 6 10 100 11.1 9.6 4.5 C 3db bw C 0.1db bw a v r l r f r g (mhz) (mhz) v s = 5v, r sd = 0 w C 1 150 562 562 48 21.4 30 649 649 34 17 10 732 732 22 12.5 1 150 619 C 54 22.3 30 715 C 36 17.5 10 806 C 22.4 11.5 2 150 576 576 48 20.7 30 649 649 35 18.1 10 750 750 22.4 11.7 10 150 442 48.7 40 19.2 30 511 56.2 31 16.5 10 649 71.5 20 10.2 C 3db bw C 0.1db bw a v r l r f r g (mhz) (mhz) v s = 5v, r sd = 0 w C 1 150 681 681 50 19.2 30 768 768 35 17 10 887 887 24 12.3 1 150 768 C 66 22.4 30 909 C 37 17.5 10 1k C 23 12 2 150 665 665 55 23 30 787 787 36 18.5 10 931 931 22.5 11.8 10 150 487 536 44 20.7 30 590 64.9 33 17.5 10 768 84.5 20.7 10.8 C 3db bw C 0.1db bw a v r l r f r g (mhz) (mhz) v s = 5v, r sd = 10.2k C 1 150 576 576 35 17 30 681 681 25 12.5 10 750 750 16.4 8.7 1 150 665 C 37 17.5 30 768 C 25 12.6 10 845 C 16.5 8.2 2 150 590 590 35 16.8 30 681 681 25 13.4 10 768 768 16.2 8.1 10 150 301 33.2 31 15.6 30 392 43.2 23 11.9 10 499 54.9 15 7.8 C 3db bw C 0.1db bw a v r l r f r g (mhz) (mhz) v s = 15v, r sd = 60.4k C 1 150 634 634 41 19.1 30 768 768 26.5 14 10 866 866 17 9.4 1 150 768 C 44 18.8 30 909 C 28 14.4 10 1k C 16.8 8.3 2 150 649 649 40 18.5 30 787 787 27 14.1 10 931 931 16.5 8.1 10 150 301 33.2 33 15.6 30 402 44.2 25 13.3 10 590 64.9 15.3 7.4
5 lt1206 typical perfor a ce characteristics wu 4 0 10 30 40 50 100 70 8 12 20 80 90 60 610 14 16 18 supply voltage (?) 3db bandwidth (mhz) lt1206 ?tpc01 peaking 0.5db peaking 5db r f = 470 w r f = 560 w r f = 680 w r f = 750 w r f = 1k r f = 1.5k a v = 2 r l = 100 w bandwidth and feedback resistance vs capacitive load for 0.5db peak capacitive load (pf) 1 100 feedback resistor ( w ) 1k 10k 100 10000 lt1206 ?tpc03 10 1000 bandwidth feedback resistor a v = 2 r l = v s = 15v c comp = 0.01 m f 1 10 100 3db bandwidth (mhz) 4 0 20 50 8 12 10 40 30 610 14 16 18 supply voltage (?) 3db bandwidth (mhz) lt1206 ?tpc02 peaking 0.5db peaking 5db r f = 560 w r f = 1k r f = 2k r f = 750 w a v = 2 r l = 10 w bandwidth vs supply voltage bandwidth vs supply voltage bandwidth vs supply voltage bandwidth vs supply voltage 4 0 10 30 40 50 100 70 8 12 20 80 90 60 610 14 16 18 supply voltage (?) 3db bandwidth (mhz) lt1206 ?tpc04 peaking 0.5db peaking 5db r f = 470 w r f = 1.5k r f = 330 w r f = 680 w r f =390 w a v = 10 r l = 100 w 4 0 20 50 8 12 10 40 30 610 14 16 18 supply voltage (?) 3db bandwidth (mhz) lt1206 ?tpc05 peaking 0.5db peaking 5db r f = 560 w r f = 1k r f = 1.5k r f = 680 w a v = 10 r l = 10 w supply voltage (?) 5 differential phase (deg) 0.30 0.40 0.50 13 lt1206 ?tpc07 0.20 0.10 0 7 9 11 15 r f = r g = 560 w a v = 2 n package r l = 15 w r l = 50 w r l = 30 w r l = 150 w supply voltage (?) 5 differential gain (%) 0.06 0.08 0.10 13 lt1206 ?tpc08 0.04 0.02 0 7 9 11 15 r f = r g = 560 w a v = 2 n package r l = 15 w r l = 30 w r l = 150 w r l = 50 w spot noise voltage and current vs frequency frequency (hz) 10 1 10 100 100 100k lt1206 ?tpc09 1k 10k spot noise (nv/ ? hz or pa/ ? hz) i n e n ? n differential gain vs supply voltage differential phase vs supply voltage bandwidth and feedback resistance vs capacitive load for 5db peak capacitive load (pf) feedback resistor ( w ) 1 lt1206 ?tpc06 10 100 1k 10k 0 3db bandwidth (mhz) 1k 10k 0 100 10 100 1 feedback resistor bandwidth a v = +2 r l = v s = ?5v c comp = 0.01 m f
6 lt1206 supply current vs ambient temperature, v s = 15v supply current vs supply voltage output short-circuit current vs junction temperature supply current vs large signal output frequency (no load) typical perfor a ce characteristics wu 4 10 12 16 18 22 8 12 14 24 20 610 14 16 18 supply voltage (?) supply current (ma) lt1206 ?tpc10 t j = 40?c t j = 25?c t j = 85?c t j = 125?c v s/d = 0v temperature (?) ?0 0 supply current (ma) 10 25 0 50 75 lt1206 ?tpc12 5 20 15 ?5 25 100 125 a v = 1 r l = n package r sd = 0 w r sd = 60.4k r sd = 121k supply current vs shutdown pin current input common-mode limit vs junction temperature temperature (?) ?0 0.7 0.8 1.0 25 75 lt 1206 ?tpc15 0.6 0.5 ?5 0 50 100 125 0.4 0.3 0.9 output short-circuit current (a) sourcing sinking output saturation voltage vs junction temperature frequency (hz) 20 power supply rejection (db) 40 60 70 10k 1m 10m 100m lt1206 ?tpc17 0 100k 50 30 10 r l = 50 w v s = 15v r f = r g = 1k negative positive power supply rejection ratio vs frequency supply current vs ambient temperature, v s = 5v frequency (hz) 10k supply current (ma) 40 50 60 100k 1m 10m lt1206 ?tpc18 30 20 10 a v = 2 r l = v s = 15v v out = 20v p-p temperature (?) ?0 v output saturation voltage (v) 1 3 4 ? 75 v + lt1206 ?tpc16 2 0 125 ? ? ? 50 ?5 100 25 v s = ?5v r l = 2k r l = 50 w r l = 50 w r l = 2k temperature (?) ?0 v common-mode range (v) 0.5 1.5 2.0 2.0 75 v + lt1206 ?tpc14 1.0 0 125 1.5 1.0 0.5 50 ?5 100 25 shutdown pin current ( m a) 0 supply current (ma) 12 16 20 400 lt1206 ?tpc11 8 4 0 100 200 300 500 10 14 18 6 2 v s = ?5v temperature (?) ?0 0 supply current (ma) 10 25 0 50 75 lt1206 ?tpc11 5 20 15 ?5 25 100 125 a v = 1 r l = n package r sd = 0 w r sd = 10.2k r sd = 22.1k
7 lt1206 2nd and 3rd harmonic distortion vs frequency output impedance vs frequency typical perfor a ce characteristics wu output impedance in shutdown vs frequency frequency (hz) 0.1 output impedance ( w ) 1 10 100 100k 10m 100m lt1206 ?tpc19 0.01 1m v s = ?5v i o = 0ma r s/d = 121k r s/d = 0 w frequency (mhz) 1 ?0 distortion (dbc) ?0 ?0 ?0 ?0 ?0 310 lt1206 ?tpc21 ?0 2456789 v s = ?5v v o = 2v p-p 2nd 3rd r l = 10 w 2nd 3rd r l = 30 w frequency (mhz) 0 10 3rd order intercept (dbm) 20 30 40 50 60 5 10 15 20 lt1206 ?tpc22 25 30 v s = 15v r l = 50 w r f = 590 w r g = 64.9 w test circuit for 3rd order intercept + 50 w lt1206 lt1206 ?tpc23 65 w 590 w p o measure intercept at p o 3rd order intercept vs frequency frequency (hz) 100 output impedance ( w ) 1k 10k 100k 100k 10m 100m lt1206 ?tpc20 10 1m a v = 1 r f = 1k v s = 15v
8 lt1206 si plified sche atic ww lt1206 ?tc v output v + 50 w d2 d1 v v + v + v c c r c comp ?n +in shutdown 1.25k to all current sources q11 q15 q9 q6 q5 q2 q1 q18 q17 q3 q4 q7 q8 q12 q16 q14 q13 q10 u s a o pp l ic at i wu u i for atio the lt1206 is a current feedback amplifier with high output current drive capability. the device is stable with large capacitive loads and can easily supply the high currents required by capacitive loads. the amplifier will drive low impedance loads such as cables with excellent linearity at high frequencies. feedback resistor selection the optimum value for the feedback resistors is a function of the operating conditions of the device, the load imped- ance and the desired flatness of response. the typical ac performance tables give the values which result in the highest 0.1db and 0.5db bandwidths for various resistive loads and operating conditions. if this level of flatness is not required, a higher bandwidth can be obtained by use of a lower feedback resistor. the characteristic curves of bandwidth vs supply voltage indicate feedback resistors for peaking up to 5db. these curves use a solid line when the response has less than 0.5db of peaking and a dashed line when the response has 0.5db to 5db of peaking. the curves stop where the response has more than 5db of peaking. for resistive loads, the comp pin should be left open (see section on capacitive loads). capacitive loads the lt1206 includes an optional compensation network for driving capacitive loads. this network eliminates most of the output stage peaking associated with capacitive loads, allowing the frequency response to be flattened. figure 1 shows the effect of the network on a 200pf load. without the optional compensation, there is a 5db peak at 40mhz caused by the effect of the capacitance on the output stage. adding a 0.01 m f bypass capacitor between the output and the comp pins connects the compensation and completely eliminates the peaking. a lower value feedback resistor can now be used, resulting in a response
9 lt1206 u s a o pp l ic at i wu u i for atio frequency (mhz) 1 ? voltage gain (db) ? 0 4 8 10 100 lt1206 ?f01 ? ? 2 6 10 12 v s = ?5v r f = 1.2k compensation r f = 2k no compensation r f = 2k compensation figure 1. which is flat to 0.35db to 30mhz. the network has the greatest effect for c l in the range of 0pf to 1000pf. the graph of maximum capacitive load vs feedback resistor can be used to select the appropriate value of feedback resistor. the values shown are for 0.5db and 5db peaking at a gain of 2 with no resistive load. this is a worst case condition, as the amplifier is more stable at higher gains and with some resistive load in parallel with the capaci- tance. also shown is the C 3db bandwidth with the sug- gested feedback resistor vs the load capacitance. although the optional compensation works well with capacitive loads, it simply reduces the bandwidth when it is connected with resistive loads. for instance, with a 30 w load, the bandwidth drops from 55mhz to 35mhz when the compensation is connected. hence, the compensation was made optional. to disconnect the optional compensa- tion, leave the comp pin open. shutdown/current set if the shutdown feature is not used, the shutdown pin must be connected to ground or v C . the shutdown pin can be used to either turn off the biasing for the amplifier, reducing the quiescent current to less than 200 m a, or to control the quiescent current in normal operation. the total bias current in the lt1206 is controlled by the current flowing out of the shutdown pin. when the shut- down pin is open or driven to the positive supply, the part is shut down. in the shutdown mode, the output looks like a 40pf capacitor and the supply current is typically 100 m a. the shutdown pin is referenced to the positive supply through an internal bias circuit (see the simplified sche- matic). an easy way to force shutdown is to use open drain (collector) logic. the circuit shown in figure 2 uses a 74c904 buffer to interface between 5v logic and the lt1206. the switching time between the active and shut- down states is less than 1 m s. a 24k pull-up resistor speeds up the turn-off time and insures that the lt1206 is completely turned off. because the pin is referenced to the positive supply, the logic used should have a break- down voltage of greater than the positive supply voltage. no other circuitry is necessary as the internal circuit limits the shutdown pin current to about 500 m a. figure 3 shows the resulting waveforms. lt1206 ? f3 a v = 1 r f = 825 w r l = 50 w r pu = 24k v in = 1v p-p figure 3. shutdown operation + lt1206 s/d 15v 15v r f r g v in 5v 24k enable v out lt1206 ?f02 15v 74c906 figure 2. shutdown interface enable v out
10 lt1206 u s a o pp l ic at i wu u i for atio slew rate unlike a traditional op amp, the slew rate of a current feedback amplifier is not independent of the amplifier gain configuration. there are slew rate limitations in both the input stage and the output stage. in the inverting mode, and for higher gains in the noninverting mode, the signal amplitude on the input pins is small and the overall slew rate is that of the output stage. the input stage slew rate is related to the quiescent current and will be reduced as the supply current is reduced. the output slew rate is set by the value of the feedback resistors and the internal capacitance. larger feedback resistors will reduce the slew rate as will lower supply voltages, similar to the way the bandwidth is reduced. the photos (figures 5a, 5b and 5c) show the large-signal response of the lt1206 for various gain configurations. the slew rate varies from 860v/ m s for a gain of 1, to 1400v/ m s for a gain of C 1. lt1206 ? f05a r f = 825 w r l = 50 w v s = 15v figure 5a. large-signal response, a v = 1 figure 5b. large-signal response, a v = C1 lt1206 ? f05b r f = rg = 750 w r l = 50 w v s = 15v for applications where the full bandwidth of the amplifier is not required, the quiescent current of the device may be reduced by connecting a resistor from the shutdown pin to ground. the quiescent current will be approximately 40 times the current in the shutdown pin. the voltage across the resistor in this condition is v + C 3v be . for example, a 60k resistor will set the quiescent supply current to 10ma with v s = 15v. the photos (figures 4a and 4b) show the effect of reducing the quiescent supply current on the large-signal response. the quiescent current can be reduced to 5ma in the inverting configuration without much change in response. in noninverting mode, however, the slew rate is reduced as the quiescent current is reduced. lt1206 ? f04a r f = 750 w r l = 50 w i q = 5ma, 10ma, 20ma v s = 15v lt1206 ? f04b r f = 750 w r l = 50 w i q = 5ma, 10ma, 20ma v s = 15v figure 4b. large-signal response vs i q , a v = 2 figure 4a. large-signal response vs i q , a v = C1
11 lt1206 figure 5c. large-signal response, a v = 2 when the lt1206 is used to drive capacitive loads, the available output current can limit the overall slew rate. in the fastest configuration, the lt1206 is capable of a slew rate of over 1v/ns. the current required to slew a capacitor at this rate is 1ma per picofarad of capacitance, so 10,000pf would require 10a! the photo (figure 6) shows the large signal behavior with c l = 10,000pf. the slew rate is about 60v/ m s, determined by the current limit of 600ma. lt1206 ? f06 figure 6. large-signal response, c l = 10,000pf v s = 15v r f = rg = 3k r l = differential input signal swing the differential input swing is limited to about 6v by an esd protection device connected between the inputs. in normal operation, the differential voltage between the input pins is small, so this clamp has no effect; however, in the shutdown mode the differential swing can be the same as the input swing. the clamp voltage will then set the maximum allowable input voltage. to allow for some margin, it is recommended that the input signal be less than 5v when the device is shut down. capacitance on the inverting input current feedback amplifiers require resistive feedback from the output to the inverting input for stable operation. take care to minimize the stray capacitance between the output and the inverting input. capacitance on the invert- ing input to ground will cause peaking in the frequency response (and overshoot in the transient response), but it does not degrade the stability of the amplifier. power supplies the lt1206 will operate from single or split supplies from 5v (10v total) to 15v (30v total). it is not necessary to use equal value split supplies, however the offset voltage and inverting input bias current will change. the offset voltage changes about 500 m v per volt of supply mis- match. the inverting bias current can change as much as 5 m a per volt of supply mismatch, though typically the change is less than 0.5 m a per volt. thermal considerations the lt1206 contains a thermal shutdown feature which protects against excessive internal (junction) tempera- ture. if the junction temperature of the device exceeds the protection threshold, the device will begin cycling be- tween normal operation and an off state. the cycling is not harmful to the part. the thermal cycling occurs at a slow rate, typically 10ms to several seconds, which depends on the power dissipation and the thermal time constants of the package and heat sinking. raising the ambient tem- perature until the device begins thermal shutdown gives a good indication of how much margin there is in the thermal design. for surface mount devices heat sinking is accomplished by using the heat spreading capabilities of the pc board and its copper traces. experiments have shown that the heat spreading copper layer does not need to be electri- cally connected to the tab of the device. the pcb material can be very effective at transmitting heat between the pad area attached to the tab of the device, and a ground or u s a o pp l ic at i wu u i for atio lt1206 ? f04c r f = 750 w r l = 50 w
12 lt1206 copper area copper area power plane layer either inside or on the opposite side of the board. although the actual thermal resistance of the pcb material is high, the length/area ratio of the thermal resistance between the layer is small. copper board stiff- eners and plated through holes can also be used to spread the heat generated by the device. tables 1 and 2 list thermal resistance for each package. for the to-220 package, thermal resistance is given for junc- tion-to-case only since this package is usually mounted to a heat sink. measured values of thermal resistance for several different board sizes and copper areas are listed for each surface mount package. all measurements were taken in still air on 3/32" fr-4 board with 1oz copper. this data can be used as a rough guideline in estimating thermal resistance. the thermal resistance for each appli- cation will be affected by thermal interactions with other components as well as board size and shape. table 1. r package, 7-lead dd thermal resistance topside* backside board area (junction-to-ambient) 2500 sq. mm 2500 sq. mm 2500 sq. mm 25 c/w 1000 sq. mm 2500 sq. mm 2500 sq. mm 27 c/w 125 sq. mm 2500 sq. mm 2500 sq. mm 35 c/w *tab of device attached to topside copper table 2. s8 package, 8-lead plastic soic thermal resistance topside* backside board area (junction-to-ambient) 2500 sq. mm 2500 sq. mm 2500 sq. mm 60 c/w 1000 sq. mm 2500 sq. mm 2500 sq. mm 62 c/w 225 sq. mm 2500 sq. mm 2500 sq. mm 65 c/w 100 sq. mm 2500 sq. mm 2500 sq. mm 69 c/w 100 sq. mm 1000 sq. mm 2500 sq. mm 73 c/w 100 sq. mm 225 sq. mm 2500 sq. mm 80 c/w 100 sq. mm 100 sq. mm 2500 sq. mm 83 c/w *pins 1 and 8 attached to topside copper y package, 7-lead to-220 thermal resistance (junction-to-case) = 5 c/w n8 package, 8-lead dip thermal resistance (junction-to-ambient) = 100 c/w calculating junction temperature the junction temperature can be calculated from the equation: t j = (p d q ja ) + t a where: t j = junction temperature t a = ambient temperature p d = device dissipation q ja = thermal resistance (junction-to ambient) as an example, calculate the junction temperature for the circuit in figure 7 for the n8, s8, and r packages assuming a 70 c ambient temperature. u s a o pp l ic at i wu u i for atio figure 7. thermal calculation example the device dissipation can be found by measuring the supply currents, calculating the total dissipation, and then subtracting the dissipation in the load and feedback network. p d = (39ma 30v) C (12v) 2 /(2k||2k) = 1.03w then: t j = (1.03w 100 c/w) + 70 c = 173 c for the n8 package t j = (1.03w 65 c/w) + 70 c = 137 c for the s8 with 225 sq. mm topside heat sinking t j = (1.03w 35 c/w) + 70 c = 106 c for the r package with 100 sq. mm topside heat sinking since the maximum junction temperature is 150 c, the n8 package is clearly unacceptable. both the s8 and r packages are usable. + 15v 15v 0.01 m f 2k 330 w 2k 300pf 12v 12v f = 2mhz 39ma i lt1206 ?f07 lt1206 s/d
13 lt1206 typical applicatio s u + lt1097 + lt1206 v in s/d comp 0.01 m f 3k 330 w 10k 1k out output offset: < 500 m v slew rate: 2v/ m s bandwidth: 4mhz stable with c l < 10nf lt1206 ?ta03 500pf + lt1115 1 m f 15v 1 m f 15v 68pf 1 m f 15v 1 m f + lt1206 0.01 m f 15v 560 w 560 w 909 w 100 w r l output r l = 32 w v o = 5v rms thd + noise = 0.0009% at 1khz = 0.004% at 20khz small signal 0.1db bandwidth = 600khz lt1206 ?ta04 s/d + + + + + lt1206 s/d ?5v 15v 24k 10k 5v 2n3904 lt1206 ?ta05 + lt1206 s/d 0.01 m f* v out r f ** v in lt1206 ?ta07 optional, use with capacitive loads value of r f depends on supply voltage and loading. select from typical ac performance table or determine empirically * ** comp precision 10 hi current amplifier low noise 10 buffered line driver cmos logic to shutdown interface buffer a v = 1 + lt1206 s/d 75 w v in r f r g 75 w 75 w 75 w 75 w 75 w cable lt1206 ?ta06 distribution amplifier
14 lt1206 package descriptio u dimensions in inches (millimeters) unless otherwise noted. n8 package 8-lead plastic dip dd7 0693 0.022 ?0.005 (0.559 ?0.127) 0.105 ?0.008 (2.667 ?0.203) 0.004 +0.008 0.004 () 0.102 +0.203 0.102 0.050 ?0.012 (1.270 ?0.305) 0.059 (1.499) typ 0.050 ?0.008 (1.270 ?0.203) 0.175 ?0.008 (4.445 ?0.203) 0.060 (1.524) 0.401 ?0.015 (10.185 ?0.381) 15?typ 0.030 ?0.008 (0.762 ?0.203) 0.331 +0.012 0.020 () 8.407 +0.305 0.508 0.143 +0.012 0.020 () 3.632 +0.305 0.508 0.050 ?0.010 (1.270 ?0.254) r package 7-lead plastic dd n8 0392 0.045 ?0.015 (1.143 ?0.381) 0.100 ?0.010 (2.540 ?0.254) 0.065 (1.651) typ 0.045 ?0.065 (1.143 ?1.651) 0.130 ?0.005 (3.302 ?0.127) 0.020 (0.508) min 0.018 ?0.003 (0.457 ?0.076) 0.125 (3.175) min 12 3 4 87 6 5 0.250 ?0.010 (6.350 ?0.254) 0.400 (10.160) max 0.009 ?0.015 (0.229 ?0.381) 0.300 ?0.320 (7.620 ?8.128) 0.325 +0.025 0.015 +0.635 0.381 8.255 ()
15 lt1206 information furnished by linear technology corporation is believed to be accurate and reliable. however, no responsibility is assumed for its use. linear technology corporation makes no represen- tation that the interconnection of circuits as described herein will not infringe on existing patent rights. package descriptio u dimensions in inches (millimeters) unless otherwise noted. s8 package 8-lead plastic soic y package 7-lead to-220 0.147 ?0.155 (3.73 ?3.94) dia 0.390 ?0.410 (9.91 ?10.41) 0.045 ?0.055 (1.14 ?1.40) 0.235 ?0.258 (5.97 ?6.55) 0.026 ?0.036 (0.66 ?0.91) 0.103 ?0.113 (2.62 ?2.87) y7 0893 0.260 ?0.320 (6.60 ?8.13) 0.045 ?0.055 (1.14 ?1.40) 0.169 ?0.185 (4.29 ?4.70) 0.095 ?0.115 (2.41 ?2.92) 0.155 ?0.195 (3.94 ?4.95) 0.620 (15.75) typ 0.560 ?0.590 (14.22 ?14.99) 0.016 ?0.022 (0.41 ?0.56) 0.700 ?0.728 (17.78 ?18.49) 0.135 ?0.165 (3.43 ?4.19) 0.152 ?0.202 (3.86 ?5.13) 1 2 3 4 0.150 ?0.157 (3.810 ?3.988) 8 7 6 5 0.189 ?0.197 (4.801 ?5.004) 0.228 ?0.244 (5.791 ?6.197) 0.016 ?0.050 0.406 ?1.270 0.010 ?0.020 (0.254 ?0.508) 45 0 8?typ 0.008 ?0.010 (0.203 ?0.254) so8 0392 0.053 ?0.069 (1.346 ?1.752) 0.014 ?0.019 (0.355 ?0.483) 0.004 ?0.010 (0.101 ?0.254) 0.050 (1.270) bsc
16 lt1206 linear technology corporation 1630 mccarthy blvd., milpitas, ca 95035-7487 (408) 432-1900 l fax : (408) 434-0507 l telex : 499-3977 ? linear technology corporation 1993 lt/gp 0993 10k rev 0 ? printed in usa world headquarters linear technology corporation 1630 mccarthy blvd. milpitas, ca 95035-7487 phone: (408) 432-1900 fax: (408) 434-0507 u.s. area sales offices northeast region linear technology corporation one oxford valley 2300 e. lincoln hwy.,suite 306 langhorne, pa 19047 phone: (215) 757-8578 fax: (215) 757-5631 linear technology corporation 266 lowell st., suite b-8 wilmington, ma 01887 phone: (508) 658-3881 fax: (508) 658-2701 southwest region linear technology corporation 22141 ventura blvd. suite 206 woodland hills, ca 91364 phone: (818) 703-0835 fax: (818) 703-0517 northwest region linear technology corporation 782 sycamore dr. milpitas, ca 95035 phone: (408) 428-2050 fax: (408) 432-6331 southeast region linear technology corporation 17060 dallas parkway suite 208 dallas, tx 75248 phone: (214) 733-3071 fax: (214) 380-5138 central region linear technology corporation chesapeake square 229 mitchell court, suite a-25 addison, il 60101 phone: (708) 620-6910 fax: (708) 620-6977 international sales offices france linear technology s.a.r.l. immeuble "le quartz" 58 chemin de la justice 92290 chatenay malabry france phone: 33-1-41079555 fax: 33-1-46314613 germany linear techonolgy gmbh untere hauptstr. 9 d-85386 eching germany phone: 49-89-3197410 fax: 49-89-3194821 japan linear technology kk 5f yz bldg. 4-4-12 iidabashi, chiyoda-ku tokyo, 102 japan phone: 81-3-3237-7891 fax: 81-3-3237-8010 korea linear technology korea branch namsong building, #505 itaewon-dong 260-199 yongsan-ku, seoul korea phone: 82-2-792-1617 fax: 82-2-792-1619 singapore linear technology pte. ltd. 101 boon keng road #02-15 kallang ind. estates singapore 1233 phone: 65-293-5322 fax: 65-292-0398 taiwan linear technology corporation rm. 801, no. 46, sec. 2 chung shan n. rd. taipei, taiwan, r.o.c. phone: 886-2-521-7575 fax: 886-2-562-2285 united kingdom linear technology (uk) ltd. the coliseum, riverside way camberley, surrey gu15 3yl united kingdom phone: 44-276-677676 fax: 44-276-64851 06/24/93

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